CN110677046B - Peak current analog-digital control system and method for flyback power supply in DCM mode - Google Patents
- ️Tue Jun 16 2020
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- CN110677046B CN110677046B CN201910898838.XA CN201910898838A CN110677046B CN 110677046 B CN110677046 B CN 110677046B CN 201910898838 A CN201910898838 A CN 201910898838A CN 110677046 B CN110677046 B CN 110677046B Authority
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- flyback power
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
- H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
- H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
- H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33515—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
- H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
- H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
- H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a peak current mode digital control system and method for a flyback power supply in a DCM (discontinuous conduction mode), and belongs to the technical field of power generation, power transformation or power distribution. According to the method, an in-phase auxiliary winding for sampling the input voltage of the flyback power supply is added, the waveform analysis is carried out on the deviation of the in-phase auxiliary winding voltage of the flyback power supply and the flyback power supply input voltage analog sampling value to calculate the high level time length that the in-phase auxiliary winding voltage exceeds the flyback power supply input voltage analog sampling value, the flyback power supply input voltage digital sampling value is updated according to the change of the high level time length, the updated input voltage digital sampling value is taken as the calculation basis of the switching tube conduction time, the extra power consumption introduced by a sampling resistor can be eliminated, the control precision is improved, and the instability introduced due to false triggering is eliminated.
Description
技术领域technical field
本发明涉及反激开关电源，尤其涉及用于DCM模式下反激电源的峰值电流模数字控制系统及方法，属于发电、变电或配电的技术领域。The invention relates to a flyback switching power supply, in particular to a peak current analog-digital control system and method for a flyback power supply in a DCM mode, and belongs to the technical field of power generation, transformation or distribution.
背景技术Background technique
开关电源通常作为各类用电设备的电源，将未调整的交流或直流输入电压变换为调整后的交流或直流输出电压。随着消费电子市场的不断繁荣以及第三代半导体技术的逐渐成熟，开关电源正在朝高频化、小型化的高功率密度的方向发展。The switching power supply is usually used as the power supply for various electrical equipment, converting the unregulated AC or DC input voltage into the adjusted AC or DC output voltage. With the continuous prosperity of the consumer electronics market and the gradual maturity of the third-generation semiconductor technology, switching power supplies are developing in the direction of high frequency, miniaturization and high power density.
目前，开关电源的控制方式主要分为两类：电压模控制和峰值电流模控制。电压模控制是单一控制环，调试简单，易于实现，并且占空比调节不受限制，缺点是输出电压的动态性能不好。在当今要求较高的开关电源需求下，电压模控制逐渐被抛弃。由于峰值电流模控制是双环控制系统，电压外环控制电流内环，电流内环是顺势快速工作的，所以峰值电流控制模式对输入电压和输出负载的响应速度均比较快。鉴于以上优点，峰值电流模控制方法被广泛应用。At present, the control methods of switching power supply are mainly divided into two categories: voltage mode control and peak current mode control. Voltage mode control is a single control loop, which is simple to debug, easy to implement, and has unlimited duty cycle adjustment. The disadvantage is that the dynamic performance of the output voltage is not good. With today's demanding switching power supply needs, voltage mode control is gradually being abandoned. Because the peak current mode control is a double-loop control system, the voltage outer loop controls the current inner loop, and the current inner loop works quickly with the trend, so the response speed of the peak current control mode to the input voltage and output load is relatively fast. In view of the above advantages, the peak current mode control method is widely used.
现有的传统峰值电流模数字控制系统框图如图1所示，峰值电流Vpeak由数字控制模块给出的Vpeak_D数模转换后输入至比较器。通过在功率开关管S下方串联一个采样电阻Rs，其压降Vcs即反应电感电流峰值，然后将Vcs输入至比较器。比较器比较两个输入信号Vpeak和Vcs的大小，并将结果close再反馈给数字控制器，数字控制模块close判断是否关闭功率管S。A block diagram of an existing traditional peak current analog-to-digital control system is shown in Figure 1. The peak current Vpeak is input to the comparator after digital-to-analog conversion by Vpeak_D given by the digital control module. By connecting a sampling resistor Rs under the power switch tube S in series, the voltage drop Vcs of it reflects the peak value of the inductor current, and then Vcs is input to the comparator. The comparator compares the magnitudes of the two input signals Vpeak and Vcs, and feeds the result close to the digital controller, and the digital control module close judges whether to close the power tube S.
上述传统的峰值电流模数字控制方法中，由于功率开关管S存在寄生电容，Rs两端的电压在功率开关管发生开关动作时存在严重的振荡与电压尖峰。采用采样电阻实现峰值电流控制有三个主要弊端：1)可能会导致功率开关管的误触发，降低了系统稳定性；2)采用串联电阻Rs对电感峰值电流进行采样会产生较大的功耗；3)由于工艺精度问题，采样电阻存在较大的误差降低控制精度；4)由于比较器和DAC的延时，系统动态响应相对于所提出的控制方法较差。In the above-mentioned traditional peak current analog-digital control method, due to the parasitic capacitance of the power switch S, the voltage across Rs has serious oscillations and voltage spikes when the power switch switches on and off. The use of sampling resistors to achieve peak current control has three main drawbacks: 1) It may lead to false triggering of the power switch tube, which reduces the system stability; 2) The use of series resistance Rs to sample the peak current of the inductor will result in greater power consumption; 3) Due to the problem of process accuracy, there is a large error in the sampling resistor, which reduces the control accuracy; 4) Due to the delay of the comparator and the DAC, the dynamic response of the system is poorer than the proposed control method.
上述问题在高频的开关电源中更加凸显，因此有必要对传统的峰值电流模数字控制方法进行改进。The above problems are more prominent in high-frequency switching power supplies, so it is necessary to improve the traditional peak current analog-digital control method.
本发明旨在提出一种新型的峰值电流模数字控制方法以消除采样电阻引入的额外功耗和误触发，提高控制精度并增加动态响应速度。The invention aims to propose a novel peak current analog-digital control method to eliminate the extra power consumption and false triggering introduced by the sampling resistor, improve the control precision and increase the dynamic response speed.
发明内容SUMMARY OF THE INVENTION
本发明的发明目的是针对上述背景技术的不足，提供了用于DCM模式下反激电源的峰值电流模数字控制系统及方法，消除采样电阻引入的额外功耗，提高控制精度，同样消除由于误触发而引入的不稳定性，解决了传统峰值电流数字模控制方法会导致功率开关管的误触发、产生较大功耗以及动态响应较差的技术问题。The purpose of the present invention is to address the deficiencies of the above-mentioned background technology, to provide a peak current analog-digital control system and method for a flyback power supply in a DCM mode, to eliminate the extra power consumption introduced by the sampling resistor, improve the control accuracy, and also eliminate errors due to errors. The instability introduced by triggering solves the technical problems that the traditional peak current digital-analog control method will cause false triggering of the power switch tube, large power consumption and poor dynamic response.
本发明为实现上述发明目的采用如下技术方案：The present invention adopts following technical scheme for realizing above-mentioned purpose of invention:
一种用于DCM模式下反激电源的峰值电流模数字控制方法，通过基于采样模块、误差计算模块、PID模块、Ton计算模块、PWM模块、驱动模块构成的控制系统实现，该系统与受控的开关电源连接起来构成一个闭环。A peak current analog-digital control method for a flyback power supply in a DCM mode is implemented by a control system based on a sampling module, an error calculation module, a PID module, a Ton calculation module, a PWM module, and a drive module. The switching power supplies are connected to form a closed loop.
采样模块对辅助绕组电压波形的分析结果进行模数转换后作为辅助绕组电压参考量的，辅助绕组电压参考量用于辅助绕组电压的反馈控制采样得到输出电压和输入电压。其中，输出电压的采样方法是传统的双线采样，为现有技术，此处不再赘述。采样模块对输入电压采样的思想是：通过比较器，对同相辅助绕组电压的波形分析结果进行模数转换后作为同相辅助绕组电压参考量，对同相辅助绕组电压与其参考值的差值进行高电平时长计时。通过判断当前采样周期高电平时长和上个采样周期高电平时长的大小来调整输入电压采样值，达到最终采样输入电压的目的。The sampling module performs analog-to-digital conversion on the analysis result of the auxiliary winding voltage waveform as the auxiliary winding voltage reference. The auxiliary winding voltage reference is used for the feedback control sampling of the auxiliary winding voltage to obtain the output voltage and input voltage. Among them, the sampling method of the output voltage is the traditional two-wire sampling, which is the prior art, and will not be repeated here. The idea of sampling the input voltage by the sampling module is: through the comparator, the waveform analysis result of the in-phase auxiliary winding voltage is converted into analog-to-digital value as the reference value of the in-phase auxiliary winding voltage, and the difference between the in-phase auxiliary winding voltage and its reference value is calculated. Usually long time. The input voltage sampling value is adjusted by judging the high-level duration of the current sampling period and the high-level duration of the previous sampling period, so as to achieve the purpose of finally sampling the input voltage.
误差计算模块的输入信号是输出信号采样值，对输出电压采样值与参考基准电压求差得到误差信号，并将差值输出给PID模块。The input signal of the error calculation module is the sampled value of the output signal. The error signal is obtained by calculating the difference between the sampled value of the output voltage and the reference reference voltage, and the difference is output to the PID module.
PID模块的输入信号为误差计算模块输出的误差信号，通过PID的自动补偿输出电感峰值电流。The input signal of the PID module is the error signal output by the error calculation module, and the peak current of the inductor is output through the automatic compensation of the PID.
功率开关管导通时间计算模块的输入信号为输入电压采样值和电感峰值电流，通过数学运算得到功率开关管导通时间。The input signal of the power switch tube conduction time calculation module is the input voltage sampling value and the inductor peak current, and the power switch tube conduction time is obtained through mathematical operations.
PWM模块的输入信号为功率开关管导通时间，输出功率开关管的占空比控制信号。The input signal of the PWM module is the conduction time of the power switch tube, and the output duty cycle control signal of the power switch tube.
驱动模块将PWM模块输出的信号转变为能够驱动功率开关管的占空比信号，控制功率开关管的导通与截止。The driving module converts the signal output by the PWM module into a duty cycle signal capable of driving the power switch tube, and controls the turn-on and turn-off of the power switch tube.
本发明采用上述技术方案，具有以下有益效果：The present invention adopts the above-mentioned technical scheme, and has the following beneficial effects:
(1)本发明提出的峰值电流模数字控制方法无需采样电阻，能够消除由于电阻引入的额外功耗，消除由于振荡而引起的不稳定，避免由于采样电阻的误差引入的控制精度的降低。(1) The peak current analog-digital control method proposed by the present invention does not require a sampling resistor, which can eliminate the extra power consumption caused by the resistance, eliminate the instability caused by the oscillation, and avoid the reduction of the control accuracy caused by the error of the sampling resistance.
(2)本发明基于波形分析和模数转换提出了一种反激电源输入电压的采样方法，通过对同相辅助绕组电压测量值和输入电压模拟采样值的偏差进行波形分析，统计各采样周期偏差信号的高电平时长，根据连续采样周期内偏差信号高电平时长的变化情况更新输入电压数字采样值，以更新后的输入电压数字采样值为开关管导通时间的计算依据，提高系统的动态响应。(2) The present invention proposes a method for sampling the input voltage of a flyback power supply based on waveform analysis and analog-to-digital conversion. By performing waveform analysis on the deviation between the measured value of the in-phase auxiliary winding voltage and the analog sampling value of the input voltage, the deviation of each sampling period is counted. The high-level duration of the signal, update the digital sampling value of the input voltage according to the change of the high-level duration of the deviation signal in the continuous sampling period, and use the updated digital sampling value of the input voltage as the basis for calculating the on-time of the switch to improve the system's performance. Dynamic Response.
(3)相对于传统的峰值电流模数字控制方法，本发明将传统峰值电流模数字控制方式中的DAC(模数转换器)和比较器用来采样输入电压Vin，仅引入了一路变压器辅助绕组，相对于高精度的采样电阻，电路的成本有所下降。(3) Compared with the traditional peak current analog-digital control method, the present invention uses the DAC (analog-to-digital converter) and the comparator in the traditional peak current analog-digital control method to sample the input voltage Vin, and only introduces a transformer auxiliary winding, Compared with the high-precision sampling resistor, the cost of the circuit is reduced.
附图说明Description of drawings
图1是传统峰值电流数字控制系统的框图。Figure 1 is a block diagram of a conventional peak current digital control system.
图2是本发明公开的峰值电流数字控制系统的框图。FIG. 2 is a block diagram of the peak current digital control system disclosed in the present invention.
图3是采样模块的内部原理图。Figure 3 is the internal schematic diagram of the sampling module.
图4是采样的输入电压的工作波形图。FIG. 4 is a working waveform diagram of the sampled input voltage.
图5是输入电压采样算法的流程图。Figure 5 is a flowchart of the input voltage sampling algorithm.
图6(a)是采用传统峰值电流模数字控制方法时反激电源动态响应的仿真结果，图6(b)是采用本发明无采样电阻峰值电流莫数字控制方法时反激电源动态响应的仿真结果。Fig. 6(a) is the simulation result of the dynamic response of the flyback power supply when the traditional peak current analog-digital control method is adopted, and Fig. 6(b) is the simulation result of the dynamic response of the flyback power supply when the digital control method of the peak current without sampling resistor of the present invention is adopted result.
具体实施方式Detailed ways
下面结合附图对发明的技术方案进行详细说明。The technical solutions of the invention will be described in detail below with reference to the accompanying drawings.
采样模块用于对输出电压Vo和输入电压Vin进行采样，其内部电路原理图如图3所示。其中，对输出电压的采样利用已有技术实现，即双线采样，在此处就不再赘述。对输入电压的采样为本发明第一次提出，如图3所示。其工作波形如图4所示Vaux2是Vaux1的反相波形，Vaux1用于输出电压Vo的采样，Vaux2用于输入电压Vin的采样。当Duty＝1，即开关管S打开时，若不考虑变压器漏感的影响，变压器原边电压为输入电压Vin，此时辅助绕组的电压Vaux2可表示为：The sampling module is used to sample the output voltage Vo and the input voltage Vin, and the schematic diagram of its internal circuit is shown in Figure 3. Among them, the sampling of the output voltage is realized by using the existing technology, that is, two-wire sampling, which will not be repeated here. The sampling of the input voltage is proposed for the first time in the present invention, as shown in FIG. 3 . As shown in FIG. 4 , its working waveform Vaux2 is the inverted waveform of Vaux1 , Vaux1 is used for sampling the output voltage Vo, and Vaux2 is used for the sampling of the input voltage Vin. When Duty=1, that is, when the switch S is turned on, if the influence of the leakage inductance of the transformer is not considered, the primary voltage of the transformer is the input voltage Vin, and the voltage Vaux2 of the auxiliary winding can be expressed as:
其中，Na为变压器辅助绕组匝数，Np为变压器原边匝数。因此，只要采样此时的Vaux2，即可得到输入电压Vin的大小：Among them, Na is the number of turns of the auxiliary winding of the transformer, and Np is the number of turns of the primary side of the transformer. Therefore, as long as Vaux2 is sampled at this time, the magnitude of the input voltage Vin can be obtained:
具体采样方法如下：辅助绕组电压Vaux2接在比较器的同相端，DAC的输出电压Ve接在比较器的反相端，比较结果为dx，并对信号dx的高电平时长进行计数，记为countx。若countx(n)>0，则Vin(n+1)＝Vin(n)+1；若countx(n-1)＝0且countx(n)＝0，则Vin(n+1)＝Vin(n)-1；若countx(n-1)>0且countx(n)＝0，则Vin(n+1)＝(Vin(n)+Vin(n-1))/2。整个采样算法可以总结为图5所示的程序流程图。The specific sampling method is as follows: the auxiliary winding voltage Vaux2 is connected to the non-inverting terminal of the comparator, the output voltage Ve of the DAC is connected to the inverting terminal of the comparator, the comparison result is dx, and the high level duration of the signal dx is counted, recorded as countx. If countx(n)>0, then Vin(n+1)=Vin(n)+1; if countx(n-1)=0 and countx(n)=0, then Vin(n+1)=Vin( n)-1; if countx(n-1)>0 and countx(n)=0, then Vin(n+1)=(Vin(n)+Vin(n-1))/2. The entire sampling algorithm can be summarized as the program flow chart shown in Figure 5.
误差计算模块把采样模块得到的输出电压Vo与参考电压求差，并把结果er输出给PID模块。The error calculation module calculates the difference between the output voltage Vo obtained by the sampling module and the reference voltage, and outputs the result er to the PID module.
PID模块根据误差计算模块的输出er进行自动补偿调节，输出峰值电流Ipeak，并输出给Ton计算模块。The PID module performs automatic compensation adjustment according to the output er of the error calculation module, outputs the peak current Ipeak, and outputs it to the Ton calculation module.
Ton计算模块的输入信号有采样模块输出的Vin和PID模块输出的Ipeak。根据反激变换器的工作原理可知，当功率开关管S打开时，电感上的电流线性上升，上升斜率为
其中，Vin为输入电压，Lm为变压器励磁电感大小，Ton为功率开关管导通时间，Ipeak为PID模块输出的峰值电流。Ton计算模块根据式(3)计算Ton：Among them, Vin is the input voltage, Lm is the magnetizing inductance of the transformer, Ton is the conduction time of the power switch, and Ipeak is the peak current output by the PID module. The Ton calculation module calculates Ton according to formula (3):
Ton计算模块将计算结果输出给PWM模块。The Ton calculation module outputs the calculation result to the PWM module.
PWM模块的输入信号为Ton，内部计算电路根据Ton设定功率开关管的导通时间。The input signal of the PWM module is Ton, and the internal calculation circuit sets the conduction time of the power switch tube according to Ton.
驱动模块将PWM模块输出的信号Duty_S转变为能够驱动功率开关管的信号Duty，控制功率开关管的导通与截止。The driving module converts the signal Duty_S output by the PWM module into a signal Duty that can drive the power switch tube, and controls the turn-on and turn-off of the power switch tube.
图6(a)、图6(b)是20V-5A反激变换器在传统峰值电流模数字控制和无采样电阻峰值电流模数字控制中动态响应的仿真结果，负载切换顺序均为100％至50％再至100％。在重载切轻载时，恢复时间从1000us改进为100us，过冲电压从2000mv改进为400mv；在轻载切重载时，恢复时间从900us改进为160us，下冲电压从2000mv改进为450mv。由上述仿真结果可以看出，动态性能大幅度提升。Figure 6(a) and Figure 6(b) are the simulation results of the dynamic response of the 20V-5A flyback converter in traditional peak current analog-digital control and peak current analog-digital control without sampling resistor, the load switching sequence is 100% to 100% 50% to 100%. When switching from heavy load to light load, the recovery time is improved from 1000us to 100us, and the overshoot voltage is improved from 2000mv to 400mv; when light load is switched to heavy load, the recovery time is improved from 900us to 160us, and the undershoot voltage is improved from 2000mv to 450mv. It can be seen from the above simulation results that the dynamic performance is greatly improved.
以上内容是结合具体的优选实施方式对本发明所作的进一步详细说明，不能认定本发明的具体实施只局限于这些说明，在此描述的本发明可以有许多变化(如，用于有源钳位反激变换器)，这种变化不能人为偏离本发明的精神和范围。因此，所有对本领域技术人员显而易见的改变，都包括在本权利要求书的涵盖范围之内。The above content is a further detailed description of the present invention in conjunction with specific preferred embodiments, and it cannot be considered that the specific implementation of the present invention is limited to these descriptions. such changes cannot artificially deviate from the spirit and scope of the present invention. Accordingly, all modifications obvious to those skilled in the art are included within the scope of the present claims.
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Application publication date: 20200110 Assignee: SUZHOU POWERON IC DESIGN Co.,Ltd. Assignor: SOUTHEAST University Contract record no.: X2022320000130 Denomination of invention: Peak current mode digital control system and method for flyback power supply in DCM mode Granted publication date: 20200616 License type: Common License Record date: 20220707 |